扬声器系统函数的测量

设扬声器是线性定常系统。它的系统函数H(ω)可以用振幅特性A(ω)和相位特性φ(ω)或群时延特性τ(ω)来表示: H(ω)=A(ω)·exp[jφ(ω)]     

在一个磁通量子内dc Josephson电流阶梯或振荡效应的物理本质

本文分析了放置于高Q谐振腔中的Josephson结、双结SQUID和单结超导环,当其Josephson频率ω=2eV₀/h和腔的本征频率相等时,Josephson电流在一个磁通量子内可以产生多次阶梯或振荡的物理本质。指出对于Josephson结或双结SQUID,当ω=ω_r时,被激发起的腔的本征振荡将反馈辐照结或SQUID,反馈场的频率作用使Josephson电流产生一般地感应台阶;而反馈场的振幅是受到外磁场调制的,当这种调制作用使反馈场振幅的空间部分与辐射场的空间部分匹配时,则引起电流在一个磁通量子内产生一系列的新的阶跃。对单结超导环,当nω=ω_r时,被激发起的腔的振荡反馈辐照作用将迫使其超流电流产生周期小于φ₀的振荡。 关键词：     

矢量介子φ的动力学模型及耦合常数f_(φK■)~2,f_(ωK■)~2与f_(ρK■)~2的值

假设矢量介子φ(Ι=0,ι=1,m_φ=7.30m_π)是K散射交换ρ,ω以及φ介子本身而形成的共振。应用双色散关系中的N/D方法,并设ρ,ω以及交换的φ介子的质量为已知,近似求出K的分波散射振幅。当要求该振幅能重新给出正确的共振位置(φ的质量)和宽度时,即可得出偶合常数f_(ρκ)、f_(ωκ)与f_(φκ)所必需满足的关系,从而给出它们可能取的数值。     

矢量介子φ的动力学模型及耦合常数fφKK2,fωKK2与fρKK2的值

假设矢量介子φ(Ι=0,ι=1,m_φ=7.30m_π)是K散射交换ρ,ω以及φ介子本身而形成的共振。应用双色散关系中的N/D方法,并设ρ,ω以及交换的φ介子的质量为已知,近似求出KK的分波散射振幅。当要求该振幅能重新给出正确的共振位置(φ的质量)和宽度时,即可得出偶合常数f_φKK²、f_ωKK²与f_ρKK²所必需满足的关系,从而给出它们可能取的数值。     

调频讯号的一些特性

一.引言 在调频制中调频电流的方程为或者,将此式展成包合载频及旁频的形式如下:其中f_0是载频,F是调制频率,△f_0是调制频率偏移,决定放于调制讯号的振幅而与调制频率F无关,J_n(x)是第一种第n阶的贝塞耳函数。如取下面的记号:     

换能器间距对SAW器件特性的影响

如以如H_i(ω)(i=1,2)表示输入输出换能器(含匹配电路)的频率特性,R_i(ω)(i=1,2)表示二者对声表面波的反射系数,T(ω)表示声表面波传播路径的频率特性,则声表面波器件的主信号响应、三次行程信号(TTE)响应以及考虑了TTE影响之后器件的总响应分别为: H_d(ω)=H_1(ω)H_2(ω)T(ω) (1) TTE(ω)=H_1(ω)H_2(ω)T~3(ω)R_1(ω)R_2(ω) (2) H(ω)=H_d(ω)+TTE(ω)=H_d(ω)[1+T~2(ω)R_1(ω)R_2(ω)(3) 设/R_i(ω)/=r_i(ω),arg{R_i(ω)}=φ_i(ω)。二者与外电路有关。在良好匹配下,r_i(ω_0)=1/2(通常小于此值),在调谐情况下运用,φ_i(ω_0)=π。通常r_i(ω)≤r_i(ω_0),且随着频偏的增大而减小的速度大于H_i(ω)。如以两换能器间的间距为x,则一般情况下T(ω)=Texp[jωx/v](v为基片中声表面波的速度)。T<1,且随x的增大而降低。但一般器件x为几十个波长,故T总是接近于1而变化不大。如令 θ(ω)=2ωx/v+φ_1(ω)+φ_2(ω) (4)     

电磁驱动的固定弦振动的理论分析

对电磁驱动的弦线波动方程进行分析,得到了严格的理论解。很好地解释了实际中出现的几个现象,并且讨论了驻波振幅与磁场和讯号源的依赖关系。结果表明：驻波振劝的振幅与讯号源的电压或电流正比,与磁场的关系依赖于电磁阴尼和空气阻尼的相对大小。     

振动与波中的两个问题讨论

一、如何唯一决定简谐振动中的初相在普通物理课本中,一般都说根据下式可以决定初相: tgφ=-v_0/(ωX_0) (1)φ——初相;v_0——初始速度;X_0——初始位置;ω——圆频率。但是,对于每一个正切值,φ都有两个解φ_1,φ_2。故由(1)式便不能唯一地决定初相了。我们又知道,初相也可以由X_0=Acosφ(2)即cosφ=X_0/A (2′)来决定。但这样决定的φ也有两个解φ_1~′,φ_2~′。我们注意到φ_1,φ_2中和φ_1~′,φ_2~′中只有一个是共同的,另一个是不同的。真正的初相应同时满足(1)和(2′)。所以,要想唯一地决定初相,应由(1)和(2′)联合起来解,同时满足(1)和(2′)的φ便是真正的初相,它也是唯一的。     

高频引力波对环形波导中电磁波的调制作用

讨论了垂直入射的、频率为ω_g的平面高频引力波对环形波导管中频率为ω_e的电磁波的调制作用．一般情况下，在波导管中与引力波传播方向垂直的对称平面附近，电磁波的能流密度会出现三种新的频率成分（2ω_e±ω_g）和ω_g．在ω_g》ω_e时，能流密度振幅的相对调制量与引力波的无量纲振幅h₀数量级相同．特别是当ω_g，ω_e和电磁波绕波导传播的绕行频率ω₀满足关系ω_g＝2ω_e》ω₀时，由于类似于共振的机制，能流密度会出现比h₀大几个数量级的振幅相对调制量．这个结果不会由于参数的微小改变而消失，这对于探测极微弱的引力辐射信号将是十分重要的 关键词：     

图解法用于受迫振动实验的定量研究

用Origin科学作图,线性拟合得到自由振动下摆轮振幅θ与固有周期T₀的关系θ=10429-6525T₀,为后续实验图像的解析提供明确参考。分别使用逐差法和图解法处理阻尼振动和幅频特性的实验数据,得阻尼系数β为0.059 4 s^-1和0.061 0 s^-1。受迫振动幅频和相频特性曲线的拟合结果显示,当电机频率ω与摆轮固有频率ω₀相等时发生共振,振幅θ_r达144°,摆轮与强迫力的相位差φ_r为90°,很好验证了相关物理实验规律。解析共振处的特征参数,算出共振圆频率ω_r=3.985 9 s^-1,与系统固有频率ω₀(3.986 8s^-1)之间的相对误差仅0.023%,说明图解法用于《受迫振动》实验数据的定量分析与计算是非常成功的。     

The influence of carrier level and frequency on modulation and beat-detection thresholds for sinusoidal carriers

This paper is concerned with modulation and beat detection for sinusoidal carriers. In the first experiment, temporal modulation transfer functions (TMTFs) were measured for carrier frequencies between 1 and 10 kHz. Modulation rates covered the range from 10 Hz to about the rate equaling the critical bandwidth at the carrier frequency. In experiment 2, TMTFs for three carrier frequencies were obtained as a function of the carrier level. In the final experiment, thresholds for the detection of either the lower or the upper modulation sideband (beat detection) were measured for "carrier" frequencies of 5 and 10 kHz, using the same range of modulation rates as in experiment 1. The TMTFs for carrier frequencies of 2 kHz and higher remained flat up to a modulation rate of about 100-130 Hz and had similar values across carrier frequencies. For higher rates, modulation thresholds initially increased and then decreased rapidly, reflecting the subjects' ability to resolve the sidebands spectrally. Detection thresholds generally improved with increasing carrier level, but large variations in the exact level dependence were observed, across subjects as well as across carrier frequencies. For beat rates up to about 70 Hz (at 5 kHz) and 100 Hz (at 10 kHz), beat detection thresholds were the same for the upper and the lower sidebands and were about 6 dB higher than the level per sideband at the modulation-detection threshold. At higher rates the threshold for both sidebands increased, but the increase was larger for the lower sideband. This reflects an asymmetry in masking with more masking towards lower frequencies. Only at rates well beyond the maximum of the TMTF did detection for the lower sideband start to be better than that for the upper sideband. The asymmetry at intermediate frequency separations can be explained by assuming that detection always takes place in filters centered above the stimulus spectrum. The shape of the TMTF and the beat-detection data reflects a limitation in resolving fast amplitude variations, which must occur central to the inner-ear filtering. Its characteristic resembles that of a first-order low-pass filter with a cutoff frequency of about 150 Hz.     

新型四倍频光生毫米波矢量信号调制技术

提出一种基于双并联马赫-曾德尔调制器(MZM)的新型四倍频光生毫米波技术,并用于矢量信号调制。传统的四倍频调制技术,由于数据信号同时调制到+2,-2阶边带上,拍频检测后两个边带上数据信号会产生相位叠加,只适用于不归零码(NRZ)等强度调制格式。提出的矢量信号调制技术将数据信号调制在一个-1阶边带上,另一个+3阶边带不携带数据,在拍频检测后幅度和相位信息被正确保留。同时,四倍频模块降低了传输过程中对电和光器件的带宽需求。理论分析和仿真结果表明,通过此方法产生的携带在60GHz载波上的6.25×108 symbol/s的四相相移键控(QPSK)信号,经过20km单模光纤传输后,误差向量幅度(EVM)损耗可以忽略。     

An analysis of quasi-frequency-modulated noise and random-sideband noise as comparisons for amplitude-modulated noise

Experiments were performed to determine under what conditions quasi-frequency-modulated (QFM) noise and random-sideband noise are suitable comparisons for AM noise in measuring a temporal modulation transfer function (TMTF). Thresholds were measured for discrimination of QFM from random-sideband noise and AM from QFM noise as a function of sideband separation. In the first experiment, the upper spectral edge of the noise stimuli was at 2400 Hz and the bandwidth was 1600 Hz. For sideband separations up to 256 Hz, at threshold sideband levels for discriminating AM from QFM noise, QFM was indiscriminable from random-sideband noise. For the largest sideband separation used (512 Hz), listeners may have used within-stimulus envelope correlation in the QFM noise to discriminate it from the random-sideband noise. Results when stimulus bandwidth was varied suggest that listeners were able to use this cue when the carrier was wider than a critical band, and the sideband separation approached the carrier bandwidth. Within-stimulus envelope correlation was also present in AM noise, and thus QFM noise was a suitable comparison because it made this cue unusable and forced listeners to use across-stimulus envelope differences. When the carrier bandwidth was less than a critical band or was wideband, QFM noise and random-sideband noise were equally suitable comparisons for AM noise. When discrimination thresholds for QFM and random-sideband noise were converted to modulation depth and modulation frequency, they were nearly identical to those for discrimination of AM from QFM noise, suggesting that listeners were using amplitude modulation cues in both cases.     

The continuous wave electron paramagnetic resonance experiment revisited

When the modulation frequency used in continuous wave electron paramagnetic resonance (cw EPR) spectroscopy exceeds the linewidth, modulation sidebands appear in the spectrum. It is shown theoretically and experimentally that these sidebands are actually multiple photon transitions, sigma(+)+kxpi, where one microwave (mw) sigma(+) photon is absorbed from the mw radiation field and an arbitrary number k of radio frequency (rf) pi photons are absorbed from or emitted to the modulation rf field. Furthermore, it is demonstrated that both the derivative shape of the lines in standard cw EPR spectra and the distortions due to overmodulation are caused by the unresolved sideband pattern of these lines. The single-photon transition does not even give a contribution to the first-harmonic cw EPR signal. Multiple photon transitions are described semiclassically in a toggling frame and their existence is proven using second quantization. With the toggling frame approach and perturbation theory an effective Hamiltonian for an arbitrary sideband transition is derived. Based on the effective Hamiltonians an expression for the steady-state density operator in the singly rotating frame is derived, completely describing all sidebands in all modulation frequency harmonics of the cw EPR signal. The relative intensities of the sidebands are found to depend in a very sensitive way on the actual rf amplitude and the saturation of single sidebands is shown to depend strongly on the effective field amplitude of the multiple photon transitions. By comparison with the analogous solutions for frequency-modulation EPR it is shown that the field-modulation and the frequency-modulation technique are not equivalent. The experimental data fully verify the theoretical predictions with respect to intensities and lineshapes.     

Photon Generation Scheme of 32-Fold Millimeter-Wave Signal Based on Mach-Zehnder Modulator

This paper proposes a 32-tupling frequency millimeter-wave (MMW) filter-free system based on four Mach-Zehnder Modulators (MZM) connected in parallel and cascaded with a simple radio-fiber (RoF) link structure. The four MZMs are all at the maximum transmission point (MATP), and the radio frequency (RF) driving voltage phase difference between MZMs is π /2. The center carrier is suppressed by using an optical attenuator (OATT) and an optical phase shifter (OPS). Two parallel MZMs can generate ±8th order and ±12th order optical sidebands, and the ±4th order optical sidebands can be suppressed by adjusting the modulation index m of the MZM, using cascaded two dual-parallel MZMS(DPMZM) and the phase difference of the RF signal source is π/4 to generate ±16th order optical sidebands. The theoretical analysis and simulation experiments are performed for the scheme proposed in this paper. The results show that the simulated and theoretical values of the optical sideband suppression ratio (OSSR) for ±16th order optical sideband signals are 60.02 and 59.96 dB, respectively, and the simulated and theoretical values of the RF sideband suppression ratio (RFSSR) for the 32-tupling MMW signal are 56.34 and 53.94 dB, respectively.     

High carrier suppression double sideband modulation using polarization state rotation filter and optical external modulator

We propose a high carrier suppression double sideband modulation technique using a Mach-Zehnder modulator (MZM) and an integrated polarization state rotation filter (PSRF), which is designed to improve the carrier suppression ratio. With the functions of MZM and PSRF, about 30 dB carrier suppression ratio relative to first-order sidebands is demonstrated. Moreover, we demonstrate the optical generation of microwave/millimeter-wave signals by beating the carrier suppressed double sideband (DSB-SC) lightwave signals. The experimental results show that the improvement of carrier suppression ratio with PSRF can effectively cancel the modulating RF frequency component. A tunable and high purity microwave signal, which is limited by the bandwidth of MZM and photodetector (PD), is obtained, and it does not suffer from obvious phase noise degradation with 25 km transmission.     

Nonlinear ultrasonic wave modulation for online fatigue crack detection

This study presents a fatigue crack detection technique using nonlinear ultrasonic wave modulation. Ultrasonic waves at two distinctive driving frequencies are generated and corresponding ultrasonic responses are measured using permanently installed lead zirconate titanate (PZT) transducers with a potential for continuous monitoring. Here, the input signal at the lower driving frequency is often referred to as a ‘pumping’ signal, and the higher frequency input is referred to as a ‘probing’ signal. The presence of a system nonlinearity, such as a crack formation, can provide a mechanism for nonlinear wave modulation, and create spectral sidebands around the frequency of the probing signal. A signal processing technique combining linear response subtraction (LRS) and synchronous demodulation (SD) is developed specifically to extract the crack-induced spectral sidebands. The proposed crack detection method is successfully applied to identify actual fatigue cracks grown in metallic plate and complex fitting-lug specimens. Finally, the effect of pumping and probing frequencies on the amplitude of the first spectral sideband is investigated using the first sideband spectrogram (FSS) obtained by sweeping both pumping and probing signals over specified frequency ranges.     

相位调制边带失衡问题研究

 高功率激光系统中一般利用相位调制器对单纵模激光进行频谱展宽以避免受激布里渊散射，当后继系统中的滤波器存在中心波长偏差时，则会导致相位调制产生的边带失衡，使光信号出现较为严重的高频起伏。基于前端系统模拟平台对此问题进行了数值模拟研究，结果表明滤波后的高频起伏随滤波器带宽变窄和中心波长偏差增大而加剧。分析表明0.2 nm带宽的滤波器出现0.05 nm左右的波长偏差时，将引起24.3%左右的顶部起伏。实验中根据分析将滤波器带宽从0.2 nm加大到0.4 nm，成功将脉冲顶部起伏从25.2%减小到了4.4%，对前端系统的研制起到了很好的指导作用。     

Critical modulation frequency based on detection of AM versus FM tones

The ratios between the modulation index (eta) for just noticeable FM of a sinusoidally modulated pure tone and the degree of modulation (m) for just noticeable AM at the same carrier and the same modulation frequency were measured at carrier frequencies of 0.125, 0.25, 0.5, 1, 2, 4, and 8 kHz. Signal levels were 20 dB SL and 50 dB SPL or 80 dB SPL. At low modulation frequencies, for example, 8 Hz, AM and FM elicit very different auditory sensations (i.e., a fluctuation in loudness or pitch, respectively). In this case, eta and m show different values for just noticeable modulation. Since both stimuli have almost equal amplitude spectra if eta equals m (m less than 0.3), the difference in detection thresholds reflects differences in the phase relation between carrier and sidebands in AM and FM. With increasing modulation frequency, the eta-m ratio decreases and reaches unity at a modulation frequency called the "critical modulation frequency" (CMF). At modulation frequencies above the CMF, the same modulation thresholds are obtained for AM and FM. Therefore, it can be concluded that the difference in phase between the two types of stimuli is not perceived in this range. At center frequencies below 1 kHz, where phase errors caused by headphones and ear canal presumably are small, the CMF is useful in estimating critical bandwidth.     

采用光纤拉曼放大改善1550 nm外调制有线电视系统的组合二阶失真指标

为克服长距离光纤有线电视（CATV）系统中采用高增益掺铒光纤放大器（EDFA）所带来的非线性损伤．对在残留边带调幅（AM—VSB）外调制光纤有线电视系统中采用光纤分布拉曼放大时的组合二阶失真（CSO）进行了,理论研究。根据拉曼放大对信号光强的增益作用。导出了分布拉曼放大条件下的薛定谔方程。并采用微扰法解出了存在拉曼分布放大时,残留边带调幅外调制有线电视系统中．自相位调制（SPM）导致的组合二阶失真的解析表达式。相应数值计算结果表明．相对于采用掺铒光纤放大器功放．采用相同放大倍数的分布托曼放大可使长距离系统中自相位调制导致的组合二阶失真性能改善10dB以上。因此可以得出结论：在长距离残留边带调幅凋制的有线电视系统中,采用分布式光纤拉曼放大可以较好地改善由自相位调制导致的组合二阶失真恶化。