泵浦激光器驰豫振荡噪声对光纤激光水听器的影响

对采用相位生成载波解调的光纤激光水听器系统中3kHz附近频域内固有噪声的产生机理进行了理论推导,并设计实验进行验证.首先测量得到泵浦激光器的驰豫振荡频率峰值,随后以400 Hz为间隔逐渐降低相位生成载波信号频率,观察固有噪声峰值的移动方向和大小.实验结果表明,随着载波信号频率的降低,固有噪声峰也向低频方向移动,移动间隔同样为400 Hz.可知相位生成载波解调算法中高频载波调制信号与泵浦激光器的驰豫振荡频率叠加是形成探测频谱固有噪声的主要原因.通过降低高频载波调制信号频率的方法对驰豫振荡噪声进行抑制,消除了探测频谱中的固有噪声峰,得到了较为平坦的本底噪声谱.     

基于波长调制技术的激光器调制特性研究

在流场诊断技术中,可调谐半导体吸收光谱技术（TDLAS）成为主要的诊断技术之一,其可实现非接触、原位检测。波长调制（WMS）和直接吸收(DA)是两种最常用的TDLAS气体传感方法,在目标含量很低或者极端流场环境下,波长调制技术呈现出更多的优势,检测灵敏度与直接吸收相比可以提高1～2个数量级。在近红外波长调制技术应用领域,分布反馈式（DFB）半导体激光器成为流场诊断技术的光源选择之一,无论利用谐波信号（或者归一化谐波信号）的线型拟合,还是选择谐波信号的峰值来反演流场参数,吸收模型的准确建立均十分重要。在模型建立时,激光器频率-时间响应以及光强-时间响应的准确表示尤为重要。为解决吸收模型准确建立问题,提出了一种准确测量激光器调制参数的完整方法,通过实验测量了用于探测水汽吸收的1 392和1 469 nm激光器的调制特性,研究了分布反馈式激光器的调制参数随调制幅度,调制频率以及工作温度的变化。根据该方法得到的调制参数,建立吸收模型,测得常温下空气中水汽浓度为1.97%,直接吸收方法测得浓度为1.99%,验证了该测量方法的准确性。研究表明,调制深度随调制幅度的增加线性增加,随调制频率的增加非线性单调减小,随工作温度的升高线性增加;激光器的出光强度和频率同时被调制,强度变化超前频率变化的相位,随调制幅度的变化不明显,随调制频率的增加单调增加,随工作温度的升高单调减小;归一化一次谐波振幅和二次振幅均随调制幅度的增加而增加,随调制频率的增加而减小,随工作温度的变化不明显。在吸收光谱应用领域,波长调制技术发挥的作用愈加重要,调制系数与谐波信号的峰值息息相关,在波长调制技术应用时,选取适当的调制参数,有利于得到合适的谐波信号,可通过改变调制幅度、调制频率、工作温度得到最优调制系数。研究了近红外分布反馈式半导体激光器的调制特性,该方法同样适用于不同封装和不同波段激光器调制特性的研究,利于推广吸收光谱技术在各领域的应用。     

阵列调制随机共振在微弱信号特征提取方面的应用

论述了阵列调制随机共振方法在强噪声背景下多频微弱信号特征提取中的工作原理和实现步骤;采用预先设定系统参数的多个并联非耦合随机共振单元形成阵列,将被测强噪声背景下的多频微弱信号分别与不同频率的载波进行调制,生成多个差频均为0.01Hz的信号作为各对应随机共振单元的激励信号,采用龙格-库塔算法求取各单元输出并进行频谱分析,根据0.01Hz处的信噪比判断在微弱信号中是否存在载波频率与差频值之和大小的频率分量,最后综合各个随机共振单元的检测结果生成微弱信号的频率特征向量;仿真结果表明,阵列调制随机共振在微弱信号特征提取方面效果明显,具有很好的应用前景。     

基于样本熵的听觉神经锁相机理的实验分析

锁相是指系统的响应与周期性刺激的特定相位同步的物理现象. 听觉神经的锁相对揭示人的听觉认知基本的神经机理及改善听觉感知有重要意义. 然而, 现有研究主要集中于心理物理方法和幅度谱分析, 不能有效区分包络响应和时域细节结构响应, 不能直观反映神经锁相. 本文主要利用拔靴法和离散傅里叶变换, 提出了基于样本熵的时域细节结构频率跟随响应(temporal-fine-structure-related frequency following response, FFR_T)的神经锁相值(phase locking value, PLV)计算方法, 用于分析神经物理实验数据. 两个脑电实验结果表明: FFR_T的PLV样本熵显著大于包络相关频率跟随响应(envelope-related frequency following response, FFR_E)的PLV, 且二者正交独立, 新方法能有效地分别反映听觉系统对包络和时间细节结构的锁相机理; 基频处的响应主要来源于FFR_E的锁相; 基频处, 不可分辨谐波成分包络的锁相能力优于对可分辨谐波; 基频缺失时, 畸变产物是不同的听觉神经通路的FFR_E的混合; 谐波处, FFR_E 集中于低频, FFR_T则集中于中、高频; 听觉神经元锁相能力与声源的频率可分辨性相关. FFR_T的PLV方法克服了现有FFR分析的局限性, 可用于深入研究听觉神经机理.     

豚鼠对正弦调幅波的频率辨别

当一高频纯音被另一低频正弦波调幅时,从复合声中可听到清楚并占主导的调制波音调。后者随调幅波的频率而变,其辨别阈(△f_(am))可在动物用记录皮层慢反应的方法测定。本工作系统地研究了豚鼠△f_(am)与载波频率、调制波频率、调幅深度、调幅时程、声音强度等的关系。豚鼠对调制波频率似有较好的辨别能力,刺激参数合适时△f_(am)只3—4Hz,与该种动物对纯音的频率辨别阈相近。文中对比了人和豚鼠的△f_(am),并讨论了调制波音调的感受和辩别机理。     

周期信号调制色泵噪音驱动下单模激光光强关联函数的时间演化特性

采用周期信号调制色泵噪音驱动的单模激光模型,运用线性化近似方法研究了单模激光系统光强关联函数C(t)随时间的演化关系,分析了调制信号的振幅B、频率Ω等对光强关联函数随时间演化的影响. 发现在泵噪音自关联时间τ>>1的情形下,随着调制信号频率Ω、振幅B的增加,C(t)随时间的演化为单调衰减;在τ>>1的情形下,随着调制信号频率Ω、振幅B的增加,C(t)随时间的演化均为周期性振荡衰减.     

飞秒钛宝石放大激光脉冲的载波包络相位测量与控制

通过对重复频率为1 kHz的放大飞秒激光脉冲的光谱干涉实验,结合傅里叶变换进行了载波包络相位漂移的实验研究.在此基础上利用锁相环反馈控制技术实现了对载波包络相位的精密锁定,锁定后的激光脉冲稳态相位均方根误差小于80mrad,锁定时间超过3h.同时在理论上分析了光谱干涉测量放大激光脉冲载波包络相位的原理,给出了光谱干涉信号与载波包络相位的关系. 关键词： 飞秒钛宝石放大器 载波包络相位 光谱干涉 超连续     

听觉部位学说与频率差阈

长时间以来一直认为听觉的部位学说,是无法解释频率差阈这样高达0．3％的频率分辨能力的。因而有时间学说和模式识别方法来加以说明。本文提出一种部位相关模型——邻带差值法,在部位学说和心理物理调谐曲线实验数据的基础上, 利用听觉滤波器相邻通带之间的能量分配关系,完全可以达到千分之几的纯音频率分辨能力。文中用一个标准的1/3倍频程滤波器为例,实验证明了它的可能性。这一模型也可用于语音信号的基频提取和纯音频率的精密测量。     

复合听神经动作电位与调幅刺激声包络的时序相关分析

在豚鼠用植入内听道出口处的电极记录了调幅声诱发的复合听神经动作电位，并研究了在声参数系统地变化时反应与调制波之间的时序相关性。所用的调制波有三种：频率固定的连续或短段正弦波（频率范围40Hz－5kHz），频率变化的短段正弦波及小段语音信号。其它声参数变化范围为：载波500Hz－20kHz，调制深度5％－95％，强度20－90dBSPL。对于频率固定的连续或短段正弦调制波，在大多数参数条件下，反应与调制波之间的相关系数（r）相当高：0．80－0．95，在由于参数不适当、反应幅度下降时，r相应地变小。对于频率变化的短段正弦调制波，r在0．66－0．86之间变化。当用语音信号片段作调制波时，反应与调制波之间仍存在一定的相关性（r在0．50左右变化），表明对语音信息在耳蜗水平的编码，时间模式是有效的。文中对听觉时间机理的一些理论及技术要点作了讨论。     

光探测器偏压调制技术的理论研究

为了简化和改善光载无线通信系统,提出了一种光探测器偏压调制技术,利用PIN光探测器(PIN-PD)和单行载流子光探测器(UTC-PD)的输出光电流随偏压变化的特性进行调制.采用光探测器偏置调制技术,光电探测和调制可以在一个光探测器上同时实现.研究表明当入射光功率为2.93dBm时,PIN-PD在10GHz射频副载波上的调制带宽为800 MHz,UTC-PD在150GHz射频副载波上的调制带宽为18.75GHz.调制带宽随入射光功率的增大而增大,当入射光功率为12.93dBm时,UTC-PD在150GHz射频副载波上的调制带宽可达25GHz.调制深度与正弦偏压调制信号的最小值有关.     

Detection of quasitrapezoidal frequency and amplitude modulation

It has been proposed that the detection of frequency modulation (FM) of sinusoidal carriers can be mediated by two mechanisms; a place mechanism based on FM-induced amplitude modulation (AM) in the excitation pattern, and a temporal mechanism based on phase locking in the auditory nerve. The temporal mechanism appears to be "sluggish" and does not play a role for FM rates above about 10 Hz. It also does not play a role for high carrier frequencies (above about 5 kHz). This experiment provided a further test of the hypothesis that the effectiveness of the temporal mechanism depends upon the time spent close to frequency extremes during the modulation cycle. Psychometric functions for the detection of AM and FM were measured for two carrier frequencies, 1 and 6 kHz. The modulation waveform was quasitrapezoidal. Within each modulation period, P, a time Tss was spent at each extreme of frequency or amplitude. The transitions between the extremes, with duration Ttrans had the form of a half-cycle of a cosine function. The modulation rate was 2, 5, 10, or 20 Hz, giving values of P of 500, 200, 100, and 50 ms. TSS varied from 0 ms (sinusoidal modulation) up to 160, 80, 40, or 20 ms, for rates of 2, 5, 10, and 20 Hz, respectively. The detectability of AM was not greatly affected by modulation rate or by the value of TSS, except for a slight improvement with increasing TSS for the lowest modulation rates; this was true for both carrier frequencies. For FM of the 6-kHz carrier, the pattern of results was similar to that found for AM, which is consistent with an excitation-pattern model of FM detection. For FM of the 1-kHz carrier, performance improved markedly with increasing TSS, especially for the lower FM rates; there was no change in performance with TSS for the 20-Hz modulation rate. The results are consistent with the idea that detection of FM of a 1-kHz carrier is partly mediated by a sluggish temporal mechanism. That mechanism benefits from greater time spent at frequency extremes of the modulation cycle for rates up to 10 Hz.     

The influence of carrier level and frequency on modulation and beat-detection thresholds for sinusoidal carriers

This paper is concerned with modulation and beat detection for sinusoidal carriers. In the first experiment, temporal modulation transfer functions (TMTFs) were measured for carrier frequencies between 1 and 10 kHz. Modulation rates covered the range from 10 Hz to about the rate equaling the critical bandwidth at the carrier frequency. In experiment 2, TMTFs for three carrier frequencies were obtained as a function of the carrier level. In the final experiment, thresholds for the detection of either the lower or the upper modulation sideband (beat detection) were measured for "carrier" frequencies of 5 and 10 kHz, using the same range of modulation rates as in experiment 1. The TMTFs for carrier frequencies of 2 kHz and higher remained flat up to a modulation rate of about 100-130 Hz and had similar values across carrier frequencies. For higher rates, modulation thresholds initially increased and then decreased rapidly, reflecting the subjects' ability to resolve the sidebands spectrally. Detection thresholds generally improved with increasing carrier level, but large variations in the exact level dependence were observed, across subjects as well as across carrier frequencies. For beat rates up to about 70 Hz (at 5 kHz) and 100 Hz (at 10 kHz), beat detection thresholds were the same for the upper and the lower sidebands and were about 6 dB higher than the level per sideband at the modulation-detection threshold. At higher rates the threshold for both sidebands increased, but the increase was larger for the lower sideband. This reflects an asymmetry in masking with more masking towards lower frequencies. Only at rates well beyond the maximum of the TMTF did detection for the lower sideband start to be better than that for the upper sideband. The asymmetry at intermediate frequency separations can be explained by assuming that detection always takes place in filters centered above the stimulus spectrum. The shape of the TMTF and the beat-detection data reflects a limitation in resolving fast amplitude variations, which must occur central to the inner-ear filtering. Its characteristic resembles that of a first-order low-pass filter with a cutoff frequency of about 150 Hz.     

Second-order temporal modulation transfer functions

Detection thresholds were measured for a sinusoidal modulation applied to the modulation depth of a sinusoidally amplitude-modulated (SAM) white noise carrier as a function of the frequency of the modulation applied to the modulation depth (referred to as f'm). The SAM noise acted therefore as a "carrier" stimulus of frequency fm, and sinusoidal modulation of the SAM-noise modulation depth generated two additional components in the modulation spectrum: fm-f'm and fm+f'm. The tracking variable was the modulation depth of the sinusoidal variation applied to the "carrier" modulation depth. The resulting "second-order" temporal modulation transfer functions (TMTFs) measured on four listeners for "carrier" modulation frequencies fm of 16, 64, and 256 Hz display a low-pass segment followed by a plateau. This indicates that sensitivity to fluctuations in the strength of amplitude modulation is best for fluctuation rates f'm below about 2-4 Hz when using broadband noise carriers. Measurements of masked modulation detection thresholds for the lower and upper modulation sideband suggest that this capacity is possibly related to the detection of a beat in the sound's temporal envelope. The results appear qualitatively consistent with the predictions of an envelope detector model consisting of a low-pass filtering stage followed by a decision stage. Unlike listeners' performance, a modulation filterbank model using Q values > or = 2 should predict that second-order modulation detection thresholds should decrease at high values of f'm due to the spectral resolution of the modulation sidebands (in the modulation domain). This suggests that, if such modulation filters do exist, their selectivity is poor. In the latter case, the Q value of modulation filters would have to be less than 2. This estimate of modulation filter selectivity is consistent with the results of a previous study using a modulation-masking paradigm [S. D. Ewert and T. Dau, J. Acoust. Soc. Am. 108, 1181-1196 (2000)].     

Spectral modulation detection as a function of modulation frequency, carrier bandwidth, and carrier frequency region

The present study investigates the nature of spectral envelope perception using a spectral modulation detection task in which sinusoidal spectral modulation is superimposed upon a noise carrier. The principal goal of this study is to characterize spectral envelope perception in terms of the influence of modulation frequency (cycles/octave), carrier bandwidth (octaves), and carrier frequency region (defined by lower and upper cutoff frequencies in Hz). Spectral modulation detection thresholds measured as a function of spectral modulation frequency result in a spectral modulation transfer function (SMTF). The general form of the SMTF is bandpass in nature, with a minimum modulation detection threshold in the region between 2 to 4 cycles/octave. SMTFs are not strongly dependent on carrier bandwidth (ranging from 1 to 6 octaves) or carrier frequency region (ranging from 200 to 12 800 Hz), with the exception of carrier bands restricted to very low audio frequencies (e.g., 200-400 Hz). Spectral modulation detection thresholds do not depend on the presence of random level variations or random modulation phase across intervals. The SMTFs reported here and associated excitation pattern computations are considered in terms of a linear systems approach to spectral envelope perception and potential underlying mechanisms for the perception of spectral features.     

Within- versus cross-channel mechanisms in detection of envelope phase disparity

These experiments were designed to examine the mechanism of detection of phase disparity in the envelopes of two sinusoidally amplitude-modulated (AM) sinusoids. Specifically, they were performed to determine whether detection of envelope phase disparity was consistent with processing within a single channel in which the AM tones were simply added. In the first condition, with an 8-Hz modulation frequency, phase-disparity thresholds increased sharply with an initial increase in separation of the carrier frequencies. They then remained approximately constant when the separation was an octave or above. In the second condition, with carrier pairs of 1 and 2 kHz or 1 and 3.2 kHz and a modulation frequency of 8 Hz, thresholds were little affected as the level of one carrier was decreased relative to the other. With a modulation frequency of 128 Hz, for most subjects there was more of an effect of level disparity on thresholds. In the third condition, when the modulation frequency was 8 Hz, subjects showed relatively constant thresholds whether the signals were presented monotically, dichotically, or dichotically with low- and high-pass noise. Dichotic thresholds were typically higher than monotic when the modulation frequency was 128 Hz. These results suggest that it is not necessary to have information available within a single additive channel to detect envelope phase disparity. In certain circumstances, a comparison across channels may be used to detect such disparities.     

Critical modulation frequency based on detection of AM versus FM tones

The ratios between the modulation index (eta) for just noticeable FM of a sinusoidally modulated pure tone and the degree of modulation (m) for just noticeable AM at the same carrier and the same modulation frequency were measured at carrier frequencies of 0.125, 0.25, 0.5, 1, 2, 4, and 8 kHz. Signal levels were 20 dB SL and 50 dB SPL or 80 dB SPL. At low modulation frequencies, for example, 8 Hz, AM and FM elicit very different auditory sensations (i.e., a fluctuation in loudness or pitch, respectively). In this case, eta and m show different values for just noticeable modulation. Since both stimuli have almost equal amplitude spectra if eta equals m (m less than 0.3), the difference in detection thresholds reflects differences in the phase relation between carrier and sidebands in AM and FM. With increasing modulation frequency, the eta-m ratio decreases and reaches unity at a modulation frequency called the "critical modulation frequency" (CMF). At modulation frequencies above the CMF, the same modulation thresholds are obtained for AM and FM. Therefore, it can be concluded that the difference in phase between the two types of stimuli is not perceived in this range. At center frequencies below 1 kHz, where phase errors caused by headphones and ear canal presumably are small, the CMF is useful in estimating critical bandwidth.     

Correlation of neural responses in the cochlear nucleus with low-frequency noise amplitude modulation of a tonal signal

The responses of single neurons of the cochlear nucleus of a grass frog to long tonal signals amplitude-modulated by repeat intervals of low-frequency noise have been studied. The carrier frequency always corresponded to the characteristic frequency of the studied cell (a range of 0.2 kHz–2 kHz); the modulated signal was noise in the ranges 0–15 Hz, 0–50 Hz, or 0–150 Hz. We obtained the correlation functions of the cyclic histogram reflecting the change in probability of a neuron pulse discharge (spike) during the modulation period with the shape of the signal envelope in the same period. The form of the obtained correlation functions usually does not change qualitatively with a change in carrier level or modulation depth; however, this could essentially depend of the frequency component of the modulating function. In the majority of cases, comparison of the cyclic histogram of the reaction with only the current amplitude value does not adequately reveal the signal’s time features that determine the reaction of a neuron. The response is also determined by the other sound features, primarily by the rate of the change in amplitude. The studied neurons differed among themselves, both in preference toward a certain range of modulated frequencies and in the features of the envelope that caused the cell’s response.     

Perceptual interaction between carrier periodicity and amplitude modulation in broadband stimuli: a comparison of the autocorrelation and modulation-filterbank model

Recent temporal models of pitch and amplitude modulation perception converge on a relatively realistic implementation of cochlear processing followed by a temporal analysis of periodicity. However, for modulation perception, a modulation filterbank is applied whereas for pitch perception, autocorrelation is applied. Considering the large overlap in pitch and modulation perception, this is not parsimonious. Two experiments are presented to investigate the interaction between carrier periodicity, which produces strong pitch sensations, and envelope periodicity using broadband stimuli. Results show that in the presence of carrier periodicity, detection of amplitude modulation is impaired throughout the tested range (8-1000 Hz). On the contrary, detection of carrier periodicity in the presence of an additional amplitude modulation is impaired only for very low frequencies below the pitch range (<33 Hz). Predictions of a generic implementation of a modulation-filterbank model and an autocorrelation model are compared to the data. Both models were too insensitive to high-frequency envelope or carrier periodicity and to infra-pitch carrier periodicity. Additionally, both models simulated modulation detection quite well but underestimated the detrimental effect of carrier periodicity on modulation detection. It is suggested that a hybrid model consisting of bandpass envelope filters with a ripple in their passband may provide a functionally successful and physiologically plausible basis for a unified model of auditory periodicity extraction.     

Discrimination of modulation depth of sinusoidal amplitude modulation (SAM) noise

The detection of sinusoidal amplitude modulation (SAM) provides a lower bound on the degree to which temporal information in the envelope of complex waveforms is encoded by the auditory system. The extent to which changes in the amount of modulation are discriminable provides additional information on the ability of the auditory system to utilize envelope fluctuations. Results from an experiment on the discrimination of modulation depth of broadband noise are presented. Discrimination thresholds, expressed as differences in modulation power, increase monotonically with the modulation depth of the standard, but do not obey Weber's law. The effects of carrier level and of modulation frequency are consistent with those observed in modulation detection: Changes in carrier level have little effect on modulation discrimination; changes in modulation frequency also have little effect except for standards near the modulation detection threshold. The discrimination of modulation depth is consistent with the leaky-integrator model of modulation detection for standards below--10 dB (20 log ms); for standards greater than--10 dB, the leaky integrator predicts better performance than that observed behaviorally.